Abstract
The Laser Interferometer Space Antenna aims to measure picometer changes of the 2.5 × 106 km sides of a triangular constellation of satellites. Each spacecraft hosts two telescopes that simultaneously transmit and receive laser beams measuring the constellation arms by heterodyning the received wavefronts with local references. We report an end-to-end investigation of the measurement noise due to the interaction between the telescope jitters and wavefront aberrations. With provisional design parameters, to achieve the targeted sensitivity the root-mean-square aberrations must be less than λ/65.
© 2019 Optical Society of America under the terms of the OSA Open Access Publishing Agreement
1. Introduction
The Laser Interferometer Space Antenna (LISA) – an equilateral triangle of three spacecraft with a side length of 2.5 × 106 km – aims to measure picometer changes in the distance between free-falling masses placed inside the spacecraft [1, 2]. As shown in Fig. 1, the measurement is split into two steps: i) the measurement of the test-mass motions with respect to onboard optical-benches and ii) the measurement of the spacecraft distance. To this end, each satellite is equipped with two telescopes (afocal, off-axis, beam expanders having provisional 134× magnification) that simultaneously transmit and receive 1064 nm laser beams and heterodyne the received beams with local references [3,4]. A critical aspect is the total displacement noise in a one way test-mass to test-mass link [3],
in the frequency band from 0.1 mHz to 0.1 Hz. This requirement imposes tight constraints on the phase of the received wavefront and the stability of the interfering beams. The shot noise contribution is about , and the local part of that measurement has been demonstrated in LISA Pathfinder [5].For the transmission, each telescope takes a collimated beam, with a diameter of 2.24 mm, and transforms it into a beam having a 300 mm diameter. For the reception, each telescope collects, with a 300 mm diameter aperture, the light sent by the far spacecraft and reduces it to a 2.24 mm diameter beam. Each telescope operates between a pair of conjugate pupils and maps angular motions in the sky into angular movements in an optical bench without any transverse displacement, and ideally without length instabilities.
Wavefront aberrations and telescope jitters interact and cause a measurement noise. Firstly, because of aberrations, the received wavefront deviates from sphericity. Therefore, the transmitter jitter leads to changes of received phase and, consequently, to apparent variations of the spacecraft distance [6,7]. Secondly, the receiver jitter misaligns the interfering beams and leads to phase changes of the heterodyne signal [8,9].
The wavefronts quality, both in the transmission and reception, must be good enough that the expected jitters do not cause phase noise in the heterodyne signal [3, 4]. In previous papers, we investigated separately the noise originating from the transmitter and receiver jitter [10,11].
In this paper, we build on those results and report about an end-to-end study of the measurement noise from the beam launch to the far field and from the reception to the heterodyne signal. Since the relationship between the measured and actual distances is computationally expensive, we used an analytic parametric surrogate for the phase of the heterodyne signal and its sensitivity to jitter. It takes the form of a polynomial expansion and allows for fast sampling from the possible wavefront aberrations. When studying the phase sensitivity to the jitter, it is possible to single out the root-mean-square deviation from flatness of the wavefronts as a global parameter predicting the mean noise.
Sections 2 and 3 model the far-field propagation of the transmitted wavefront and interference. Sections 4.2 and 4.3 give the polynomial approximations of the far-field and heterodyne-signal phases, which are the main results of our previous studies. Section 4.4 works on these approximations and provides the noise and sensitivity to the jitters of the heterodyne signal. In section 5 we carry out a Monte Carlo simulation of the measurement noise by sampling from random wavefront aberrations, examine how the sensitivity to the jitters depends on the design parameters and aberrations, and develop criteria for the noise assessment.
2. Far-field propagation
By using the scalar and paraxial approximations, the optical field propagating between the spacecraft is
where z is the propagation distance, r = {x, y} is a position vector in a plane transverse to the z axis, ω is the angular frequency, k = ω/c = 2π/λ is the wave number, λ = 1064 nm is the wavelength. Owing to the finite speed of light and the relative spacecraft motion, the z axis points the receiving telescope at about 16 s forward the observation direction (see Fig. 1).The complex amplitude of the transmitted beam,
is assumed to have a Gaussian intensity-profile, where wTX is the 1/e2 beam-radius and STX(r) is a small and zero-mean wavefront aberrations.The paraxial propagation in free space is given by the Rayleigh-Sommerfeld integral
where ξ is a dummy position vector in the z = 0 input plane, ℳ is the area of the primary mirror – a disk having rTX ≈ 150 mm radius – and the exp[ikξ2/(2z)] kernel factor has been included in exp[−iSTX(ξ)] as an additional defocus.We approximate the received field by the spherical wave
where ϕfar = arg[u(0; z)] is the advance or delay with respect to the dynamical phase kz, is the on-axis amplitude of the far field, and r and θ are the radial and azimuthal coordinates.3. Heterodyne interferometry
We describe the local,
and received, optical fields on the detector plane by the complex amplitudes and where we omitted the common term eiωt, z is the spacecraft distance, ϕfar is the far-field phase of the transmitted wavefront, S1(r) and S2(r) are small, zero mean, deviations from flat wavefronts, r = (x, y)T is a position vector in the detector plane, w1 and w2 are the beam radii, and Ω is the heterodyne angular frequency.In (5), due to the negligible size of the telescope aperture relative to the size of the received beam, we approximated the received wavefront by a plane one having a phase delay (or advance) ϕfar that depends on the transmission angle and aberrations. The propagation through the receiver optics introduce anew wavefront aberrations, which are summarized by S1(r).
Though they matter in terms of contrast and shot noise, the interfering-beam amplitudes do not affect the phase of the interference signal. Therefore, we set both to unity. By neglecting the piston terms of S1(r) and S2(r), we do not consider the phase retardation related to the optical lengths of the beam paths through the receiving telescope and optical bench.
The phase of the heterodyne signal is kz + ϕ, where
is the phase advance (or delay) to the dynamical one, ϕΞ = arg(Ξ), and is the interference signal. In (12), 𝒟 is the detector area (a disk having rD ≈ 1.1 mm radius), is the harmonic mean of and , SRX(r) = S2(r) − S1(r) is a small deviation from flatness of the interference-pattern phase, and r and θ are the radial and azimuthal coordinates.The ϕfar phase depends on the transmission angle α through the tilt component of STX. The transmission is on-axis and α is null when the tilt aberration of STX is zero and the transmitted beam propagates along the z axis (see Figs. 1 and 2). The ϕΞ phase depends on the reception angle β through the tilt component of SRX. The reception is on-axis and β is null when the tilt aberration of SRX is zero and the received and local beams propagate in parallel (see Figs. 1 and 2).
In (10), we assumed a Gaussian intensity profile. However, if the receiver is modelled as an ideal beam-expander, the interference is between a local Gaussian beam and a received top-hat beam. Both Gaussian and (ideal) top-hat beams are limit cases. Furthermore, ϕfar and ϕΞ require the evaluation of the same integrals (6) and (12). In the Gaussian beam limit case here considered, they differ only by the replacement of with . In the top-hat limit case, they are identical.
4. Phase noise
4.1. Zernike modes
The phase profiles STX(r) and SRX(r) are expressed in terms of Zernike modes. Therefore,
where the radial polynomial are null for all n − |m| odd or negative, ρ = |r|/rTX,D is the normalized radial coordinate, and θ is the azimuth. The Zernike polynomials satisfy the orthogonality relationTo ensure that STX,RX(r) are real, the relationship holds. Therefore, are real and, if m ≠ 0, , where . Eventually, the magnitudes are expressed in radians. The n = 1 term,
where rRX = MrD and takes the transmission, and reception, angles into account.We will also use the in-plane and out-of-plane components , , , . Similar equations hold for the ηx,y and βx,y components.
4.2. Far-field phase
By expressing STX(r) in term of Zernike modes and limiting the analysis to the lowest order couplings between tilt and higher-order aberrations, the phase of the received wavefront in advance or delay to the kz retardation is
where u(0; z) is given by (6), are the directional components of the tilt aberration of the transmitted wavefront with respect to a flat one orthogonal to the z axis, αx and αy are the directional components of the transmission angle, and rTX is the radius of the primary mirror. A null angle, i.e., α = 0, means that the transmission occurs along the z axis.The aij coefficients – which we derived in [10] – depend on the normalized radius of the transmitted beam, w′TX = wTX/rTX, and the modal amplitudes of the transmitted wavefront. By limiting the aberrations to defocus, astigmatism, coma, trefoil, and spherical, they are given in the appendix.
As shown in [7, 10], for each specific wavefront aberration STX, there exists an optimal transmission angle αopt – which can be found by solving ∇αϕfar = 0 – that nullifies the ϕfar sensitivity to the transmission angle.
4.3. Heterodyne-signal phase
To study the phase of the heterodyne signal, we express the misalignment of the interfering beams in term of the reception angle β, where β = 0 rad means that the interfering beams are parallel. Therefore, the angle β means that the tilt aberration of the phase profile SRX(r) is associated with the Mβ misalignment of the interfering beams, where M ≈ 134 is the telescope magnification.
By expressing the phase profile SRX(r) in terms of Zernike modes and limiting the analysis to the lowest order couplings between tilt and higher-order aberrations, we obtain
where Ξ is given by (12), are the directional components of the (differential) tilt aberration of the interfering wavefronts, βx and βy are the directional components of the reception angle, rRX = MrD is the effective detector radius, and rD is the detector radius.The bij coefficients – which we derived in [11] – depend on the normalized mean-radius of the interfering beams w′RX = wRX/rD and the amplitudes of the phase-profile aberrations. By limiting the aberrations to defocus, astigmatism, coma, trefoil, and spherical, they are given in the appendix. Owing to the identity of the (6) and (12) integrals, the aij and bij coefficients in (18) and (21) are linked by .
As shown in [11], for each specific aberration STX of the interference phase-profile there exists an optimal reception angle βopt – which can be found by solving ∇βϕΞ = 0 – that nullifies the ϕΞ sensitivity to the reception angle.
4.4. Phase noise
To compensate for the disturbances, the telescope pointings are continuously corrected, which corrections jitter both the transmission and reception angles and, according to (18) and (21), interfere with the phase of the heterodyne signal (see Fig. 2). The LISA error budgeting is done in the frequency domain, with noises expressed as power spectral densities. However, since no dynamics is involved in the propagation of the wavefronts, the transfer function that maps jitters into phase noise is independent of frequency. Therefore, we considered white uncorrelated jitters and computed how the jitter variance propagates into the phase-noise variance.
By linearization of (18) and (21), the variance of the ϕ = ϕfar + ϕΞ phase is
where is the variance of the jitter magnitude and ∇α,β are gradients over α and β [12]. The 1/4 factor originates from the relationship between the Rayleigh distribution of the jitter magnitude and that of its directional components.The transfer function is ℌ = σϕ/σjitter, where
the 0x and 0y subscripts label the mean values of ζx,y and ηx,y, and we used (19-b) and (22-b). Furthermore, to parameterize the result by w′TX = wTX/rTX and w′RX = wRX/rD = wTX/rRX, we neglected truncation and diffraction and used wTX = MwRX.The aij and bij coefficients depend on the amplitudes of the Zernike modes. To find a criterion for the noise assessment, we need an expression determined by the deviations of the wavefront from flatnsses alone. The sought expression can be obtained by the averaging ℌ2 over the amplitudes constrained to a predetermined root-mean-square amplitude σS of the wavefront aberrations. Therefore, the amplitudes of the Zernike modes of STX and SRX are constrained by
where if m = 0 and otherwise. In the following, we set σS = 74 mrad. The average peak-to-valley deviation from flatness of a wavefront having this root-mean-square aberration-amplitude is about λ/16, with a 15% standard deviation.By averaging over the azimuths of the amplitudes – which are assumed identical, independent, and uniformly distributed – we average over all the orientations of the Zernike modes. Since the origin is arbitrary, we can set the tilt azimuth to zero, so that the average, , cannot depend on the directional tilt-components. Hence, we obtain
where and and are the mean values of the transmission and reception angles (see Fig. 2). The polynomial coefficients were calculated analytically with the aid of Mathematica [13] by limiting the aberrations to defocus, astigmatism, coma, trefoil, and spherical. The results are where B, C, D, E, F, G, and H depend on the normalized radius w′ as given in (42-i).The average over the magnitude of the Zernike modes requires to integrate the polynomials (29-b) over the hyperellipsoid (26). A derivation of these integrals is in [14]. The result is
where According to (31), α0 = β0 = 0 rad minimize, on the average, the phase noise. Therefore, after averaging over the possible transmitter and receiver aberrations, to minimize the contributions of the jitters to the phase noise, both the transmission and reception must be on-axis. In the case of off-axis arrangements, the quadratic terms of (31) prevail. In fact, they are of the order of , while the constant ones are of the order of .5. Results
The jitter and aberrations of the transmitter and receiver contribute to the noise of the interferometric measurement. The received wavefront was approximated by a plane one whose phase ϕfar advances or delays with respect the dynamical one (encoding the sought distance) because of the transmitter jitter and aberrations. An ideal receiver – that is, a perfect compressor – does not aberrate the received wavefront, also if we take the truncation into account. The additional advance or delay ϕΞ of the signal phase takes the receiver non-ideality and jitter into account. Eventually, the average of the transfer function (25) over aberrations having the same root-mean-square amplitude summarizes the noise contributions of both the transmitter and receiver.
The asymptotic values,
are shown in Fig. 3. To quantify the dispersion of the ℌ2 values, we calculated the standard deviations of 104 g0(w′) and g2(w′) values when the angles α0 and β0 are 1 μrad and the root-mean-square amplitudes of STX and SRX is σS = 74 mrad. In practice, the azimuths , , and were drawn independently and uniformly in the [−π, +π] interval. Those of and were chosen with equal probability zero or π. Eventually, the magnitudes , , , , and were generated as independent normal variables and then projected onto the hyperellipsoid (26) [15,16]. This same procedure was used for the subsequent Monte Carlo calculations.As shown in Fig. 3, when the normalized radii of the transmitted and detected beams, w′TX = wTX/rTX and w′RX = wRX/rD tend to zero (Gaussian-beam approximation) and infinity (plane-wave approximation) the heterodyne signal is insensitive to the jitter. Also, as shown in Fig. 3 (left), the on-axis terms and of (31) do not contribute to . Figure 3 (right) shows that the off-axis terms are maximum when the normalized radii are w′TX ≈ 0.4 and w′RX ≈ 0.6, with (blue line) predominates over (red line).
The parabolic approximations (18) and (21) hold if STX,RX < 1 rad over the effective domains of the integrations (4) and (12). However, while the wavefront deviations from flatness satisfy this constraint for all practical purposes, we would like (18) and (21) to be satisfactory approximations for tilt aberrations as significant as possible. Heuristically, STX,RX < 1 rad implies or, equivalently, α < 1/(kwTX) and β < 1/(kMwRX) = 1/(kwTX). By using wTX = 150 cm, we obtain α, β ≲ 1 μrad.
To test the accuracy of the approximations made, Fig. 4 compares (18) against the numerical integration of (6). Since (6) cannot depend on the azimuth origin, we can always set and express it in term of the transmission angle α. The approximation is good up to about 1 μrad and acceptable up to about 3 μrad. It is worth noting that – since the square coefficients are of the first order, while those of the linear terms are of the second – ϕfar and ϕΞ are minimum or maximum near to the on-axis transmission/reception.
To quantify the approximation error, we calculated the fractional errors of 104 approximated ϕfar values when α0 = 2 μrad and the Zernike spectra of STX were randomly generated, but constrained to a root-mean-square amplitude σS = 74 mrad. Figure 4 shows that, on the average, (18) underestimates ϕfar by about 8%, with a standard deviation of 10%. Since it implies the same integration, the same is true for (21).
As regards the approximation (25) of ℌ2, since the calculations of ∇αϕfar and ∇βϕΞ are the same, but the width parameter of ∇βϕΞ is scaled down by , the leading ℌ2 term is ∇αϕfar (see Fig. 3, red lines vs. blue lines, and Fig. 11, w′RX axis vs. w′TX axis). Also in this case, the Zernike spectra of STX were randomly generated, but constrained to a root-mean-square amplitude σS = 74 mrad. Figure 5 compares the values of ∇αϕfar obtained from (18) against the differentiation of the numerical integration of (6). The figure shows that, when considering large transmission angles, (18) and (21) neglect significant higher-order contributions. Figure 6 shows the histogram of 104 calculations of the leading ∂αϕfar term, where ∂α is the directional derivative along α and α0 = 2 μrad. Hence, on the average, (25) underestimates ℌ by about 30%, with a standard deviation of 13%.
In the αβ plane, the contour lines of are ellipses having the axes parallel to constant transmission and reception angles. Figure 7 shows the sections β0 = 0 rad and α0 = 0 rad for varying values of the normalized radius of the transmitted and detected beams. If the normalized radius is null (Gaussian beam approximation), the heterodyne signal is insensitive to jitter. As the normalized radii grow, increases but returns to zero when the normalized radius tend to infinity (plane waves approximation). When w′TX = w′RX = 1, Fig. 7 also shows upper and lower bounds calculated as plus/minus one approximate standard deviation
where σℌ2 was obtained from 104 Monte Carlo calculations of (25).To trade off between the jitter, wavefront quality, and transmission/reception angles, Fig. 8 shows the mean jitter transfer function for varying root-mean-square deviations from flatness of the wavefronts. It also proves the agreement between the analytical and Monte Carlo averaging of ℌ2. The top axis ticks give the mean peak-to-valley deviation from flatness of each Monte Carlo set.
With about 2 μrad beam divergence and a conservative analysis of the achievable optical and alignment imperfections, to maximise the received power, the transmitter must point the receiver, to within 10 nrad [3]. Hence, the transmission angle α0 is negligible. As regards the reception angle, owing to the point-ahead angle, it cannot be null, unless the local reference is tilted with respect to the transmitted beam. The noise requirement (1) is for interfering-beam misalignments up to 300 μrad, a statement that comes from a top-level breakdown and was adopted as a conservative and rather stringent one [8,9]. Since the telescope reduces the misalignment by the magnification, a 300 μrad angle means that, in the sky, the noise requirement (1) is for reception angles β0 up to 2.2 μrad.
To cope with a jitter [3, 4], the jitter transfer function must be constrained to pm/nrad, as indicated by the dashed line in Fig. 8. By considering (31), where α0 = 0 mrad and β0 = 2 μrad, this means that the root-mean-square aberrations of the wavefronts must be constrained to 97 mrad (equivalently, to λ/65). Furthermore, if we take the dispersion (one standard deviation, see Fig. 8) into account, the the root-mean-square aberrations must be constrained to 70 mrad (equivalently, to λ/90).
To investigate how the heterodyne phase depends on the specific set of Zernike amplitudes, we calculated the |∇αϕfar|0 derivative for 104 random aberrations of the transmitted wavefront constrained by σS = 74 mrad. After sorting the results in ascending |∇αϕfar|0 order, Fig. 9 shows the |∇αϕfar|0 moving-average and Fig. 10 shows the moving average of the Zernike amplitudes and correlation of the defocus and spherical aberrations. The same results hold for the phase sensitivity to the receiver jitter, |∇βϕΞ|0.
Figure 9 shows that there is room for improvements by identifying how aberrations (having the same root-mean-square amplitude) combine constructively or destructively. Figure 10 (left) shows that a low sensitivity is correlated to small defocus and astigmatism. This is consistent with (27), because – on the average and with the w′TX = 1 choice made, see Fig. 11 – the leading g2(w′TX) term of is dominated by the coefficients of the and amplitudes. Also, a low sensitivity correlates to aberrations having the largest spherical aberration because the coefficient of the amplitude is the smallest. Figure 10 (right) shows that correlated defocus and spherical aberrations combine to keep sensitivity low. In fact, they contribute with opposite signs to (27).
6. Conclusion
Heterodyne interferometry, where laser beams are simultaneously transmitted and received by onboard telescopes, will sense the separation of the LISA spacecraft down to picometre sensitivity. Due to the interaction with the wavefront aberrations, telescope jitter affects the measured distances. In previous papers [10, 11], we developed surrogates of the far-field and heterodyne-signal phases, in the form of polynomial expansions, that allow for reduced computational loads and analytic evaluation of the measurement noise.
We build on these separate investigations by using them to map analytically the spacecraft jitter into the phase noise of the heterodyne signal. Here, we combined the wavefront aberrations and jitters in a global computation, including far-field propagation, non-ideal reception, and heterodyne detection of the accumulated phase. Also, we averaged analytically the jitter transfer function over transmission and reception aberrations constrained by given root-mean-square amplitudes and developed criteria for trading off between allocations for aberrations, jitters, designs, and operations.
After fixing the root-mean-square aberrations, the jitter-induced noise depends on the radii of the transmitted and detected beams, the telescope and detector apertures, and the transmission and reception angles. To achieve the targeted performance, using the present estimates of the radii, apertures, angles, and jitter [3,4], the root-mean-square aberrations must be less than 97 mrad (equivalently, λ/65). This figure is significantly more demanding than the present estimate [3,4].
Future calculations of the wavefront aberrations in the far field, the aberration impact on the interferometric signal, and the aberrations and jitter effect on the measurement of the spacecraft separation will require dedicated numerical tools. Our parametric surrogate is a test-bed to validate them.
Appendix: Far-field and interference phases
In [10,11], the coefficients aij and bij of the far-field and interference phases (18) and (21) have been calculated with the aid of Mathematica [13] by limiting the aberrations of the transmitted and detected wavefronts to defocus, astigmatism, coma, trefoil, and spherical. Hence,
The A2, A4, B, C, D, E, F, G, and H coefficients depend on the normalized radius w′ (see Fig. 11) where, in (18) (aij coefficients), and, in (21) (bij coefficients), Here, wTX is the 1/e2 radius of the transmitted beam and wRX is the harmonic mean of the 1/e2 radii of the interfering beams.Funding
European Space Agency (1550005721, Metrology Telescope Design for a Gravitational Wave Observatory Mission).
Disclosures
The authors declare that there are no conflicts of interest related to this article.
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